Ming Sun – Silicon achitect, design lead, researcher.

Conditions

Vin = 3.8V
Vout = -5V
R = 10Ω
L = 1µH
C = 10µF (derated)
fsw = 3MHz
Rsns = 0.3Ω
Se tracks inductor current down-slope

G_vc transfer function for PCM (peak current mode) IBB converter

A PCM controlled Boost converter is as shown in Fig. 1.

Fig. 1Gvc test bench for PCM controlled IBB converter in Simplis

We know that for a IBB converter, its right half plane zero can be expressed as:

`omega_(rhpz) = (R*D^('2))/(D*L)`

(1)

For a IBB converter, we know that:

`V_{OUT} = -V_g*D/D^'`

(2)

Therefore, duty cycle D can be calcuated to be 0.568. As a result, the right half plane zero frequency can be calculated as:

`f_(rhpz) = (R*D^('2))/(2pi*D*L) = (10*0.432^2)/(6.28*0.568*1mu) = 523kHz`

(3)

We know that right half plane zero can not be compensated in the frequency domain. This is because in order to compensate right half plane zero we need to have a right half plane pole, which does not exist in a stable circuit. Therefore, the closed loop cross over frequency of the PCM controlled Boost converter has to be less than the right half plane zero frequency. As a result, let us choose the cross over frequency to be 150kHz.

The G_vc transfer function simulated result is as shown in Fig. 2^[1].

Fig. 2Gvc simulated result from Simplis

Next, we are going to design the Type-II compensator to make the PCM Boost converter stable.

Type-II compensator design

Fig. 3 shows a Type-II compensator, where an OTA is being used^[2].

Fig. 3Type-II compensator block diagram^[3]

From Ref. [3], we can sketch the Type-II compensator transfer function as shown in Fig. 4.

Fig. 4Type-II compensator Bode plot illustration

p₁ is the dominant pole, which will make sure we have a good DC voltage accuracy at Boost converter's output. Since we have a low frequency pole due to G_vc, z₁ has to be placed inside the cross over frequency so that we can have sufficient phase margin. Let us place z₁ to be 1/3 of the cross over frequency, which is 50kHz.

First, let us choose C₁ to be 50pF and calculate the rest of the compensation network components value. If the calculated results do not quite make sense to integrate the components (resistors or capacitors) in the silicon, we can always come back to pick a new value for C₁. As a result, the resistor R₁ value can be calculated as:

`R_1 = 1/(z_1C_1) = 1/(6.28*50k*50p) = 64kΩ`

(4)

We know the mid-band gain of the Type-II compensator is g_m*R₁. To make sure the cross over frequency is at 150kHz, from Fig. 2, we know that:

`g_mR_1*alpha = 16dB`

(5)

Where, α is the resistor feedback factor. Since the IBB converter output is a negative voltage, we need to level shift it as shown in Fig. 5.